Electronic Circuitry

This application is based upon and claims the benefit of priority from the prior Japanese Patent Application No. 2024-164420, filed on Mar. 20, 2024, the entire contents of which are incorporated herein by reference.

Embodiments relate to an electronic circuitry.

A linear regulator controls an on-resistance of an output transistor provided between an input voltage line and an output terminal to reduce an input voltage and output a predetermined constant voltage. A typical linear regulator includes a current limiting circuit that limits an output current of the output transistor to a predetermined value or less. The current limiting circuit limits a variable range of a drive voltage of the output transistor within a predetermined range, thereby controlling the output current of the output transistor to be equal to or less than a predetermined value.

A voltage equivalent to a difference between the input voltage and the output voltage is applied between a drain and a source of the output transistor, but the output voltage is fixed to a constant value, whereas the input voltage can take any value equal to or greater than the output voltage. For this reason, the drain-source voltage of the output transistor changes depending on the input voltage, and the output current changes accordingly. As a result, an output current limiting function of the linear regulator has a dependency on the input voltage.

According to one embodiment, an electronic circuitry comprises a first transistor connected between an input voltage line and an output terminal, an input voltage being supplied to the input voltage line; and a current limiting circuit configured to limit an output current of the first transistor to a limiting current or less by restricting a variable range of a drive voltage of the first transistor within a predetermined range, the limiting current being determined by a reference voltage having a dependency on the input voltage.

According to one embodiment, an electronic circuitry comprises: a first transistor connected between an input voltage line and an output terminal, an input voltage being supplied to the input voltage line; a second transistor connected between the input voltage line and a first node; a current limiting circuit including a third diode-connected transistor and an error amplifier; a constant current circuit configured to keep a total of a reference current and an output current of the second transistor constant; and a first voltage fixing circuit connected to the third transistor and configured to fix a voltage of the first node to a predetermined first setting voltage.

According to one embodiment, aan electronic circuitry comprises a first transistor connected between an input voltage line and an output terminal, an input voltage being supplied to the input voltage line; a second transistor connected to the input voltage line and a first node; a third diode-connected transistor configured to generate a reference voltage by generating a reference current corresponding to the input voltage; a current limiting circuit configured to limit an output current of the first transistor to a limiting current or less by restricting a variable range of a drive voltage of the first transistor within a predetermined range, the limiting current depending on the reference voltage; a constant current circuit configured to keep a total of the reference current and an output current of the second transistor constant; and a second voltage fixing circuit configured to fix a drain-source voltage of the second transistor to a predetermined second setting voltage.

Hereinafter, embodiments will be described with reference to the drawings. In the drawings, the same or corresponding components are designated by the same reference numerals, and detailed descriptions thereof will not be given as appropriate.

Before descriptions of linear regulators according to the present embodiments, a linear regulator according to a comparative embodiment will be described and problems thereof will be discussed.

12 FIG. 700 700 1 1 3 1 1 1 1 1 2 is a diagram illustrating a configuration of a linear regulatoraccording to the comparative embodiment. The linear regulatorincludes a voltage control circuit that maintains an output voltage Vo at a predetermined constant value. The voltage control circuit includes an output transistor PM(a first transistor), resistors Rto R, an error amplifier, and a transistor NM. A source of the output transistor PMis connected to an input voltage line VDD, and a drain of the output transistor PMis connected to an output terminal Vo. The resistors Rand Rare connected in series between the output terminal Vo and a ground, and divide the output voltage Vo at a predetermined ratio to generate a divided voltage Vd.

1 1 1 1 3 1 The error amplifiercompares the divided voltage Vd with a reference voltage Vref. When the divided voltage Vd is lower than the reference voltage Vref, the error amplifieroutputs a positive voltage and the transistor NMenters an ON state. Whereby, a current flows from the input voltage line VDD through a drain-source of the transistor NMto the ground, and a voltage drop across the resistor Rincreases. As a result, a drive voltage Pdr of the output transistor PMreduces, on-resistance between the drain and the source reduces, and thus the output voltage Vo rises.

1 1 1 3 1 Conversely, when the divided voltage Vd is higher than the reference voltage Vref, the error amplifieroutputs a negative voltage and the transistor NMenters an OFF state. Whereby, a current does not flow from the input voltage line VDD through the drain-source of the transistor NMto the ground, and the voltage drop across the resistor Rdecreases. As a result, the drive voltage Pdr of the output transistor PMrises, the on-resistance between the drain and the source increases, and thus the output voltage Vo reduces.

700 By the operation of the voltage control circuit described above, the output voltage Vo of the linear regulatoris maintained at a constant value that satisfies the following relational expression.

700 1 2 2 1 3 1 1 3 1 3 LIM Further, the linear regulatorincludes a current limiting circuit that limits an output current Io of the output transistor PMto a predetermined value or less. The current limiting circuit includes an error amplifier, a transistor PM, a constant current source I, a diode-connected transistor PM(a third transistor), and a first reference current source In. By the constant current source I, a constant current Iflows from the input voltage line VDD through the resistor Rand the constant current source Ito the ground. A reference voltage Vis generated by the diode-connected transistor PMand the first reference current source In.

2 1 3 1 2 2 2 1 3 3 1 LIM LIM The error amplifiercompares the drive voltage Pdr of the output transistor PMwith the reference voltage V. When the output voltage Vo reduces and the voltage drop across the resistor Rincreases due to the operation in the case where the divided voltage Vd is lower than the reference voltage Vref as described above, the drive voltage Pdr of the output transistor PMbecomes lower than the reference voltage V, so that the output voltage of the error amplifierdecreases and the transistor PMenters an ON state. Thus, a current flows from the input voltage line VDD through a drain-source of the transistor PMand a drain-source of the transistor NMto the ground, and in exchange, the current flowing through the resistor Rstagnates and the voltage drop across the resistor Rstagnates. As a result, the decrease in the drive voltage Pdr of the output transistor PMstagnates, and the increase in the output current Io thereof is hindered.

3 1 2 2 1 LIM Conversely, when the output voltage Vo rises and the voltage drop across the resistor Rdecreases due to the operation in the case where the divided voltage Vd is higher than the reference voltage Vref as described above, the drive voltage Pdr of the output transistor PMbecomes higher than the reference voltage V, so that the output voltage of the error amplifierrises and the transistor PMenters an OFF state. As a result, the stagnation of the decrease in the drive voltage Pdr of the output transistor PMis resolved, and the increase in the output current Io thereof is not hindered.

13 FIG. 3 3 3 3 3 3 LIM is a graph illustrating voltage-current characteristics between a drain and a source of the diode-connected transistor PM. A vertical axis Idsrepresents a current between the drain and the source of the transistor PM. A horizontal axis Vdsrepresents a voltage between the drain and the source of the transistor PM. A voltage value between the drain and the source of the transistor PM, that is, the reference voltage Vis a function only of the first reference current In, which is a current value flowing between the drain and the source, and is expressed by Equation (2) below.

3 3 3 Here, Land Windicate a gate length and a gate width of the transistor PM, respectively, μp indicates positive-carrier mobility, Cox indicates a gate oxide film capacitance per unit area, and Vth indicates a threshold voltage.

14 FIG. 1 1 1 1 1 1 LIM is a graph illustrating drain-source voltage/current characteristics of the output transistor PMat a given drive voltage Pdr=V. A vertical axis Io represents a current between the drain and the source of the output transistor PM. A horizontal axis Vdsrepresents a voltage between the drain and the source of the output transistor PM. A solid line represents actual characteristics in which a channel length modulation effect exists, and a broken line represents ideal characteristics in which the channel length modulation effect does not exist. A current value between the drain and the source of the output transistor PM, that is, the output current Io, is a function of a voltage Vds, which is a voltage value between the drain and the source, and is expressed by Equation (3) below.

1 1 1 1 Here, Land Windicate a gate length and a gate width of the output transistor PM, respectively, and \indicates a channel length modulation coefficient.

1 LIM When Equation (1) is substituted into Equation (3), the output current Io of the output transistor PMis limited to a limiting current Ior less expressed by Equation (4) below.

1 1 1 In Equation (4), the drain-source voltage Vdsof the output transistor PMis a difference between the input voltage VDD and the output voltage Vo, that is, |Vds|=VDD−Vo. The output voltage Vo is fixed to a constant value, whereas the input voltage VDD can take any value equal to or greater than the output voltage Vo.

14 FIG. 14 FIG. 1 1 700 LIM LIM In the ideal characteristic (λ1=0) where the channel length modulation effect does not exist as indicated by the broken line in, Equation (4) does not depend on Vds. However, in the actual characteristic (λ1≠0) where the channel length modulation effect exists as indicated by the solid line in, Equation (4) depends on Vds, and the limiting current Ichanges as the input voltage VDD changes. Specifically, the limiting current Iincreases as the input voltage VDD increases. Therefore, the output current limiting function of the linear regulatoraccording to the comparative embodiment has a dependency on the input voltage VDD.

1 FIG. 100 100 5 6 10 2 700 5 6 6 1 is a diagram illustrating a configuration of a linear regulatoraccording to a first embodiment. The linear regulatorincludes a current mirror circuit formed by a transistor PMand a transistor PM(a second transistor) and a first voltage fixing circuitformed by a transistor NM(a fourth transistor), in addition to the components of the linear regulatoraccording to the comparative embodiment. Sources of the transistors PMand PMare connected to an input voltage line VDD. A drain of the transistor PMis connected to a first node N.

2 10 3 2 1 1 2 1 1 1 1 A drain of the transistor NMforming the first voltage fixing circuitis connected to a drain of a diode-connected transistor PM. A source of the transistor NMis connected to the first node N. A constant voltage source Vis connected to a gate of the transistor NM. The constant voltage source Vgenerates a voltage obtained by adding a threshold voltage Vth to a predetermined setting voltage Vn (first setting voltage). Accordingly, when a first reference current In flowing downstream of the first node Nis a constant value as will be described below, a change in voltage of the first node Nbecomes extremely small, and the voltage of the first node Nis substantially fixed to the setting voltage Vn. In the first embodiment, the setting voltage Vn is set to be equal to the output voltage Vo, that is, Vn=Vo. The “fixed” in the present embodiment not only means that the voltage is completely fixed to the set value, but also means that a slight change in voltage near the set value is allowed.

100 12 3 5 4 6 6 3 5 1 4 6 3 Further, the linear regulatorincludes a constant current source, a cascode current mirror circuit formed by transistors NMto NM, and a current mirror circuit formed by transistors NMand NM. A value of a drain-source current Ip of the transistor PMis determined by an aspect ratio of each of the transistors NMto NMforming the cascode current mirror circuit. A value of the first reference current In flowing downstream of the first node Nis determined by an aspect ratio of each of the transistors NMand NMforming the current mirror circuit. A second reference current Is corresponding to a difference between the first reference current In and the current Ip flows between the drain and the source of the diode-connected transistor PM.

6 6 1 6 1 1 6 A drain-source voltage Vdsof the transistor PMis a difference between the input voltage VDD and the setting voltage Vn of the first node N, that is, |Vds|=VDD−Vn. The setting voltage (Vn=Vo) of the first node Nis fixed to a constant value, whereas the input voltage VDD can take any value equal to or greater than the output voltage Vo. Therefore, similarly to the output transistor PM, the drain-source current Ip of the transistor PMdepends on the input voltage VDD, and the current Ip becomes large as the input voltage VDD becomes large.

4 6 4 6 6 1 The current mirror circuit formed by the transistors NMand NMfunctions as a constant current circuit that keeps the first reference current In at a constant value. Specifically, the transistors NMand NMare designed to have a long gate length or are formed by a plurality of cascode-connected transistors. Thus, the first reference current In flowing between the drain and the source of the transistor NMis almost not affected by the channel length modulation effect and has a constant value. Therefore, the following relationship is established among the currents Ip, Is, and In according to a current conservation law at the first node N.

2 FIG. is a graph illustrating characteristics of the currents Ip, Is, and In. A horizontal axis of the graph represents a difference between the input voltage VDD and the output voltage Vo, where the output voltage Vo is fixed to a constant value and only the input voltage VDD changes. The first reference current In does not depend on the input voltage VDD and has a constant value. The current Ip depends on the input voltage VDD, and the current Ip becomes large as the input voltage VDD becomes large. The second reference current Is also depends on the input voltage VDD, and the second reference current Is becomes small as the input voltage VDD becomes large, contrary to the current Ip.

3 FIG. 2 FIG. is a graph illustrating only the characteristics of the second reference current Is from. The second reference current Is becomes small as the input voltage VDD becomes large ((A) in the drawing), and the second reference current Is becomes large as the input voltage VDD becomes small ((B) in the drawing).

4 FIG. 3 3 3 3 LIM LIM LIM is a graph illustrating drain-source voltage/current characteristics of the diode-connected transistor PM. A drain-source voltage Vdsof the transistor PM, that is, the reference voltage V, is determined only by a drain-source current Ids, that is, the second reference current Is. Specifically, the reference voltage Vbecomes small as the second reference current Is is small ((A) in the drawing), and the reference voltage Vbecomes large as the second reference current Is is large ((B) in the drawing).

5 FIG. 1 1 1 LIM LIM LIM LIM LIM LIM is a graph illustrating drain-source voltage/current characteristics of the output transistor PM. A drain-source current Io of the output transistor PMdepends on the drive voltage Pdr and the drain-source voltage |Vds|=VDD−Vo. Therefore, the limiting current Idepends on the reference voltage Vand the input voltage VDD. Specifically, when the reference voltage Vis small, the characteristic graph shifts downward ((A) in the drawing), and when the reference voltage Vis large, the characteristic graph shifts upward ((B) in the drawing). As a result, the limiting current Iwhen the input voltage VDD is large ((A) in the drawing) is substantially equal in magnitude to the limiting current Iwhen the input voltage VDD is small ((B) in the drawing).

LIM LIM LIM LIM 100 To summarize the above operation, when the input voltage VDD is large, the second reference current Is and the reference voltage Vbecome small and the limiting current Ibecomes small. Conversely, when the input voltage VDD is small, the second reference current Is and the reference voltage Vbecome large and the limiting current IUM becomes large. In other words, when the magnitude of the input voltage VDD changes, the magnitude of the limiting current Ichanges so as to cancel out the effect of the change. Thus, the dependency of the output current limit of the linear regulatoron the input voltage VDD is reduced.

100 1 100 LIM LIM LIM LIM As described above, the linear regulatoraccording to the first embodiment includes a current limiting circuit that restricts a variable range of the drive voltage Pdr of the output transistor PMwithin a predetermined range and thereby limiting the output current Io to the limiting current Ior less. Since the second reference current Is, which determines the limiting current I, has a dependency on the input voltage VDD, the dependency of the limiting current Von the input voltage VDD is cancelled out. More specifically, a positive correlation between the limiting current Vand the input voltage VDD is cancelled out by a negative correlation between the second reference current Is and the input voltage VDD. Due to such features, the linear regulatoraccording to the first embodiment can reduce the dependency of the output current limit on the input voltage VDD.

6 26 6 1 1 6 6 1 1 6 6 1 1 6 FIG. Most preferably, a dependency characteristic of the drain-source current Ip of the transistor PMon the input voltage VDD coincides with a dependency characteristic of the output current Io on the input voltage VDD, as illustrated in. In order to do so, a channel length modulation coefficientof the transistor PMis preferably equal to a channel length modulation coefficient \of the output transistor PM. Moreover, a gate length Lof the transistor PMis preferably equal to a gate length Lof the output transistor PM. Furthermore, the drain-source voltage |Vds|=VDD−Vn of the transistor PMis preferably equal to the drain-source voltage |Vds|=VDD−Vo of the output transistor PM, that is, the setting voltage Vn of the first node Nis preferably equal to the output voltage Vo. However, even when these values are slightly different, as long as there is a rough similarity between the characteristics of the second reference current Is and the characteristics of the output current Io, the dependency of the output current limit on the input voltage VDD can be reduced.

7 FIG. 200 3 5 2 210 1 is a diagram illustrating a configuration of a linear regulatoraccording to a second embodiment. A bias voltage Vb used in a cascode current mirror circuit formed by transistors NMto NMis input to a gate of a transistor NMof a first voltage fixing circuit. Accordingly, the constant voltage source Vrequired in the first embodiment cannot be provided, and thus a circuit scale can be reduced. Further, most preferably, the bias voltage satisfies a relationship of Vb=Vo+Vth, but even when such a relationship is not perfectly satisfied, the dependency of the output current limit on the input voltage VDD can be reduced as long as such a relationship is closely satisfied.

8 FIG. 300 311 2 310 311 1 2 311 2 311 1 1 is a diagram illustrating a configuration of a linear regulatoraccording to a third embodiment. An output signal of an error amplifier(a first error amplifier) is input to a gate of a transistor NMof a first voltage fixing circuit. The error amplifieroutputs a comparison result between a voltage of a first node Nand a setting voltage Vn generated by a constant voltage source V. In detail, a positive input terminal of the error amplifieris connected to the constant voltage source Vthat generates the setting voltage Vn=Vo. A negative input terminal of the error amplifieris connected to the first node N. Accordingly, the voltage of the first node Nis fixed to the setting voltage Vn=Vo. Even with such a configuration, the dependency of the output current limit on the input voltage VDD can be reduced.

9 FIG. 400 410 7 8 7 3 7 1 8 13 8 3 1 is a diagram illustrating a configuration of a linear regulatoraccording to a fourth embodiment. A first voltage fixing circuitincludes a current mirror circuit formed by a transistor NM(a fifth transistor) and a transistor NM(a sixth transistor). A drain of the transistor NMis connected to a drain of a diode-connected transistor PM. A source of the transistor NMis connected to a first node N. A drain of the transistor NMis connected to a constant current source. A source of the transistor NMis connected to a constant voltage source Vthat generates a setting voltage Vn=Vo. Accordingly, the voltage of the first node Nis fixed to the setting voltage Vn=Vo. Even with such a configuration, the dependency of the output current limit on the input voltage VDD can be reduced.

10 FIG. 500 520 2 6 522 2 520 9 2 9 2 522 2 4 2 2 6 is a diagram illustrating a configuration of a linear regulatoraccording to a fifth embodiment. A second voltage fixing circuitfixes a voltage of a drain (a second node P) of a transistor PMto a predetermined setting voltage Vp (a second setting voltage)=Vo. In detail, an output signal of an error amplifier(a second error amplifier) is input to a gate of a transistor NMof the voltage fixing circuitand a gate of a transistor NM(a seventh transistor) that has a mirror relationship with the transistor NM. A drain of the transistor NMis connected to the second node P. The error amplifieroutputs a comparison result between the voltage of the second node Pand the setting voltage Vp generated by a constant voltage source V. Accordingly, the voltage of the second node Pis fixed to the setting voltage Vp=Vo. As a result, a drain-source voltage Vds(=VDD-Vp) of the transistor PMsatisfies VDD-Vo. Even with such a configuration, the dependency of the output current limit on the input voltage VDD can be reduced.

11 FIG. 600 620 2 6 623 7 620 7 2 7 1 623 2 5 2 2 6 is a diagram illustrating a configuration of a linear regulatoraccording to a sixth embodiment. A second voltage fixing circuitfixes a voltage of a drain (a second node P) of a transistor PMto a setting voltage Vp=Vo. In detail, an output signal of an error amplifier(a third error amplifier) is input to a gate of a transistor PM(an eighth transistor) of the voltage fixing circuit. A source of the transistor PMis connected to the second node P. A drain of the transistor PMis connected to a first node N. The error amplifieroutputs a comparison result between the voltage of the second node Pand the setting voltage Vp generated by a constant voltage source V. Accordingly, the voltage of the second node Pis fixed to the setting voltage Vp=Vo. As a result, a drain-source voltage Vds(=VDD-Vp) of the transistor PMsatisfies VDD-Vo. Even with such a configuration, the dependency of the output current limit on the input voltage VDD can be reduced.

While certain embodiments have been described, these embodiments have been presented by way of example only, and are not intended to limit the scope of the inventions. Indeed, the novel embodiments described herein may be embodied in a variety of other forms; furthermore, various omissions, substitutions and changes in the form of the embodiments described herein may be made without departing from the spirit of the inventions. The accompanying claims and their equivalents are intended to cover such forms or modifications as would fall within the scope and spirit of the inventions.

The embodiments of the present invention can also be configured as follows.

a first transistor connected between an input voltage line and an output terminal, an input voltage being supplied to the input voltage line; and a current limiting circuit configured to limit an output current of the first transistor to a limiting current or less by restricting a variable range of a drive voltage of the first transistor within a predetermined range, the limiting current being determined by a reference voltage having a dependency on the input voltage. Clause 1. An electronic circuitry comprising:

Clause 2. The electronic circuitry according to clause 1, wherein a negative correlation between the reference current and the input voltage cancels out a positive correlation between the limiting current and the input voltage.

a first transistor connected between an input voltage line and an output terminal, an input voltage being supplied to the input voltage line; a second transistor connected between the input voltage line and a first node; a current limiting circuit including a third diode-connected transistor and an error amplifier; a constant current circuit configured to keep a total of a reference current and an output current of the second transistor constant; and a first voltage fixing circuit connected to the third transistor and configured to fix a voltage of the first node to a predetermined first setting voltage. Clause 3. (first to fourth embodiments) An electronic circuitry comprising:

the second transistor has a channel length modulation coefficient equal to that of the first transistor. Clause 4. The electronic circuitry according to clause 3, wherein

the second transistor has a gate length equal to that of the first transistor. Clause 5. The electronic circuitry according to clause 3 or 4, wherein

the predetermined first setting voltage is equal to an output voltage of the output terminal. Clause 6. The electronic circuitry according to any one of clauses 3 to 5, wherein

the first voltage fixing circuit includes a fourth transistor, a source of the fourth transistor being connected to the first node, the reference current flows between a drain of the fourth transistor and the source of the fourth transistor, and the predetermined first setting voltage plus a threshold voltage is input to a gate of the fourth transistor. Clause 7. (first embodiment) The electronic circuitry according to any one of clauses 3 to 6, wherein

the first voltage fixing circuit includes a fourth transistor, a source of the fourth transistor being connected to the first node, the reference current flows between a drain of the fourth transistor and the source of the fourth transistor, and a bias voltage of a current mirror circuit is input to a gate of the fourth transistor. Clause 8. (second embodiment) The electronic circuitry according to any one of clauses 3 to 6, wherein

the first voltage fixing circuit includes: a fourth transistor having a source connected to the first node; and a first error amplifier configured to output a comparison result between the voltage of the first node and the predetermined first setting voltage, the reference current flows between a drain of the fourth transistor and the source of the fourth transistor, and an output signal of the first error amplifier is input to a gate of the fourth transistor. Clause 9. (third embodiment) The electronic circuitry according to any one of clauses 3 to 6, wherein

the first voltage fixing circuit includes a current mirror circuit formed by a fifth transistor and a sixth transistor, the reference current flows between a drain of the fifth transistor and a source of the fifth transistor, the sixth transistor has a source connected to the first node, and the predetermined first setting voltage is input to the source of the sixth transistor. Clause 10. (fourth embodiment) The electronic circuitry according to any one of clauses 3 to 6, wherein

a voltage control circuit configured to control an on-resistance of the first transistor by controlling a drive voltage of the first transistor. Clause 11. The electronic circuitry according to any one of clauses 3 to 10, further comprising

a first transistor connected between an input voltage line and an output terminal, an input voltage being supplied to the input voltage line; a second transistor connected to the input voltage line and a first node; a third diode-connected transistor configured to generate a reference voltage by generating a reference current corresponding to the input voltage; a current limiting circuit configured to limit an output current of the first transistor to a limiting current or less by restricting a variable range of a drive voltage of the first transistor within a predetermined range, the limiting current depending on the reference voltage; a constant current circuit configured to keep a total of the reference current and an output current of the second transistor constant; and a second voltage fixing circuit configured to fix a drain-source voltage of the second transistor to a predetermined second setting voltage. Clause 12. (fifth and sixth embodiments) An electronic circuitry comprising:

the second voltage fixing circuit includes: a fourth transistor having a source connected to the first node; a seventh transistor that has a mirror relationship with the fourth transistor; and a second error amplifier configured to output a comparison result between a voltage of the second node being a drain of the second transistor, and the predetermined second setting voltage, the reference current flows between a drain of the fourth transistor and the source of the fourth transistor, the seventh transistor has a drain connected to the second node, the seventh transistor has a source connected to the first node, and the fourth transistor and the seventh transistor have gates, respectively, to which an output signal of the second error amplifier is input. Clause 13. The electronic circuitry according to clause 12, wherein

the second voltage fixing circuit includes: a fourth transistor having a source connected to the first node; a third error amplifier configured to output a comparison result between a voltage of the second node being a drain of the second transistor, and the predetermined second setting voltage; and an eighth transistor having a drain connected to the first node and having a source connected to the second node, the reference current flows between a drain of the fourth transistor and the source of the fourth transistor, an output signal of the third error amplifier is input a gate of the eighth transistor. Clause 14. The electronic circuitry according to clause 12, wherein